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PDF AUR9713 Data sheet ( Hoja de datos )
| Número de pieza | AUR9713 | |
| Descripción | STEP DOWN DC-DC CONVERTER | |
| Fabricantes | BCD | |
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Data Sheet
1.5MHz, 1A, STEP DOWN DC-DC CONVERTER
AUR9713
General Description
The AUR9713 is a high efficiency step-down
DC-DC voltage converter. The chip operation is
optimized using constant frequency, peak-current
mode architecture with built-in synchronous power
MOS switchers and internal compensators to reduce
external part counts. It is automatically switching
between the normal PWM mode and LDO mode to
offer improved system power efficiency covering a
wide range of loading conditions.
The oscillator and timing capacitors are all built-in
providing an internal switching frequency of
1.5MHz that allows the use only small surface mount
inductors and capacitors for portable product
implementations. Additional features included
integrated Soft Start (SS), Under Voltage Lock OUT
(UVLO).
The device is available in adjustable output voltage
versions ranging from 1V to 3.3V, and is able to
deliver up to 1A.
The AUR9713 is available in TSOT-23-5 package.
Features
• High Efficiency Buck Power Converter
• Low Quiescent Current
• Output Current: 1A
• Adjustable Output Voltage from 1V to 3.3V
• Wide Operating Voltage Range: 2.5V to 5.5V
• Built-in Power Switches for Synchronous
Rectification with High Efficiency
• Feedback Voltage: 600mV
• 1.5MHz Constant Frequency Operation
• Automatic PWM/LDO Mode Switching Control
• Thermal Shutdown Protection
• Low Drop-out Operation at 100% Duty Cycle
• No Schottky Diode Required
Applications
• Mobile Phone, Digital Camera and MP3 Player
• Headset, Radio and Other Hand-held Instrument
• Post DC-DC Voltage Regulation
• PDA and Notebook Computer
TSOT-23-5
Mar. 2012 Rev. 1. 1
Figure 1. Package Type of AUR9713
BCD Semiconductor Manufacturing Limited
1
1 page  
Data Sheet
1.5MHz, 1A, STEP DOWN DC-DC CONVERTER
AUR9713
Electrical Characteristics
VIN=3.6V, VOUT=2.5V, VREF=0.6V, L=2.2µH, CIN=4.7µF, COUT=10µF, TA=25°C, IMAX=1A.
Parameter
Input Voltage Range
Shutdown Current
Regulated1Feedback
Voltage
Regulated Output
Voltage Accuracy
Peak
Current
Inductor
Oscillator Frequency
PMOSFET RON
NMOSFET RON
Quiescent Current
LX Leakage Current
Feedback Current
EN Leakage Current
EN High-level Input
Voltage
EN Low-Level Input
Voltage
Under Voltage Lock
Out
Hysteresis
Thermal Shutdown
Symbol
VIN
IOFF
VFB
∆VOUT/VOUT
IPK
fOSC
RON(P)
RON(N)
IQ
ILX
IFB
IEN
VEN_H
VEN_L
TSD
Conditions
Min Typ Max Unit
2.5 5.5 V
VEN=0
0.1 1 µA
For Adjustable Output Voltage 0.585 0.6 0.615 V
VIN=2.5V to 5.5V;
IOUT=0 to 1A
-3 3 %
VIN=3V, VFB=0.5V
or
VOUT=90%, Duty Cycle＜35%
1.5
A
VIN=3.6V
1.2 1.5 1.8 MHz
VIN=3.6V, IOUT=200mA
0.28 Ω
VIN=2.5V, IOUT=200mA
0.38 Ω
ILOAD=0mA, VFB=VREF+5%
100 µA
VIN=5V, VEN=0V, VLX=0V or
5V
0.01 0.1 µA
30 nA
0.01 0.1 µA
VIN=2.5V to 5.5V
1.5
V
VIN=2.5V to 5.5V
0.6 V
1.8 V
0.1 V
150 °C
Mar. 2012 Rev. 1. 1
BCD Semiconductor Manufacturing Limited
5
5 Page 
Data Sheet
1.5MHz, 1A, STEP DOWN DC-DC CONVERTER
AUR9713
Application Information (Continued)
5. Efficiency Considerations
The efficiency of switching regulator is equal to the
output power divided by the input power times 100%.
It is usually useful to analyze the individual losses to
determine what is limiting efficiency and which
change could produce the largest improvement.
Efficiency can be expressed as:
Efficiency=100%-L1-L2-…..
Where L1, L2, etc. are the individual losses as a
percentage of input power.
Although all dissipative elements in the regulator
produce losses, two major sources usually account for
most of the power losses: VIN quiescent current and
I2R losses. The VIN quiescent current loss dominates
the efficiency loss at very light load currents and the
I2R loss dominates the efficiency loss at medium to
heavy load currents.
5.1 The VIN quiescent current loss comprises two
parts: the DC bias current as given in the electrical
characteristics and the internal MOSFET switch gate
charge currents. The gate charge current results from
switching the gate capacitance of the internal power
MOSFET switches. Each cycle the gate is switched
from high to low, then to high again, and the packet
of charge, dQ moves from VIN to ground. The
resulting dQ/dt is the current out of VIN that is
typically larger than the internal DC bias current. In
continuous mode,
I GATE = f × (QP + QN )
Where QP and QN are the gate charge of power
PMOSFET and NMOSFET switches. Both the DC
bias current and gate charge losses are proportional to
the VIN and this effect will be more serious at higher
input voltages.
5.2 I2R losses are calculated from internal switch
resistance, RSW and external inductor resistance RL.
In continuous mode, the average output current
flowing through the inductor is chopped between
power PMOSFET switch and NMOSFET switch.
Then, the series resistance looking into the LX pin is
a function of both PMOSFET RDS(ON) and NMOSFET
RDS(ON) resistance and the duty cycle (D):
( )RSW = RDS (ON )P × D + RDS (ON )N × 1 − D
Therefore, to obtain the I2R losses, simply add RSW to
RL and multiply the result by the square of the
average output current.
Other losses including CIN and COUT ESR dissipative
losses and inductor core losses generally account for
less than 2 % of total additional loss.
6. Thermal Characteristics
In most applications, the part does not dissipate much
heat due to its high efficiency. However, in some
conditions when the part is operating in high ambient
temperature with high RDS(ON) resistance and high
duty cycles, such as in LDO mode, the heat
dissipated may exceed the maximum junction
temperature. To avoid the part from exceeding
maximum junction temperature, the user should do
some thermal analysis. The maximum power
dissipation depends on the layout of PCB, the thermal
resistance of IC package, the rate of surrounding
airflow and the temperature difference between
junction and ambient.
7. PCB Layout Considerations
When laying out the printed circuit board, the
following checklist should be used to optimize the
performance of AUR9713.
1) The power traces, including the GND trace, the LX
trace and the VIN trace should be kept direct, short
and wide.
2) Put the input capacitor as close as possible to the
VIN and GND pins.
3) The FB pin should be connected directly to the
feedback resistor divider.
4) Keep the switching node, LX, away from the
sensitive FB pin and the node should be kept small
area.
Mar. 2012 Rev. 1. 1
BCD Semiconductor Manufacturing Limited
11
11 Page | ||
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| PDF Descargar | [ Datasheet AUR9713.PDF ] | |
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