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PDF 5962-9459301MPA Data sheet ( Hoja de datos )
| Número de pieza | 5962-9459301MPA | |
| Descripción | 800 MHz/ 50 mW Current Feedback Amplifier | |
| Fabricantes | Analog Devices | |
| Logotipo |  |
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FEATURES
Excellent Video Specifications (RL = 150 ⍀, G = +2)
Gain Flatness 0.1 dB to 100 MHz
0.01% Differential Gain Error
0.025؇ Differential Phase Error
Low Power
5.5 mA Max Power Supply Current (55 mW)
High Speed and Fast Settling
880 MHz, –3 dB Bandwidth (G = +1)
440 MHz, –3 dB Bandwidth (G = +2)
1200 V/s Slew Rate
10 ns Settling Time to 0.1%
Low Distortion
–65 dBc THD, fC = 5 MHz
33 dBm 3rd Order Intercept, F1 = 10 MHz
–66 dB SFDR, f = 5 MHz
High Output Drive
70 mA Output Current
Drives Up to Four Back-Terminated Loads (75 ⍀ Each)
While Maintaining Good Differential Gain/Phase
Performance (0.05%/0.25؇)
APPLICATIONS
A-to-D Driver
Video Line Driver
Professional Cameras
Video Switchers
Special Effects
RF Receivers
PRODUCT DESCRIPTION
The AD8001 is a low power, high-speed amplifier designed
to operate on ±5 V supplies. The AD8001 features unique
9
6
G = +2
3 RL = 100⍀
0
–3
–6
VS = ؎5V
RFB = 820⍀
VS = ؎5V
RFB = 1k⍀
–9
–12
10M
100M
FREQUENCY – Hz
1G
Figure 1. Frequency Response of AD8001
800 MHz, 50 mW
Current Feedback Amplifier
AD8001
FUNCTIONAL BLOCK DIAGRAMS
8-Lead DIP (N-8, Q-8)
and SOIC (SO-8)
5-Lead
SOT-23-5
NC 1
8 NC
–IN 2
7 V+
+IN 3
6 OUT
V– 4 AD8001 5 NC
AD8001
VOUT 1
5 +VS
–VS 2
+IN 3
4 –IN
NC = NO CONNECT
transimpedance linearization circuitry. This allows it to drive
video loads with excellent differential gain and phase perfor-
mance on only 50 mW of power. The AD8001 is a current
feedback amplifier and features gain flatness of 0.1 dB to 100 MHz
while offering differential gain and phase error of 0.01% and
0.025°. This makes the AD8001 ideal for professional video
electronics such as cameras and video switchers. Additionally,
the AD8001’s low distortion and fast settling make it ideal for
buffer high-speed A-to-D converters.
The AD8001 offers low power of 5.5 mA max (VS = ± 5 V) and
can run on a single +12 V power supply, while being capable of
delivering over 70 mA of load current. These features make this
amplifier ideal for portable and battery-powered applications
where size and power are critical.
The outstanding bandwidth of 800 MHz along with 1200 V/µs
of slew rate make the AD8001 useful in many general purpose
high-speed applications where dual power supplies of up to ± 6 V
and single supplies from 6 V to 12 V are needed. The AD8001 is
available in the industrial temperature range of –40°C to +85°C.
Figure 2. Transient Response of AD8001; 2 V Step, G = +2
REV. C
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700 World Wide Web Site: http://www.analog.com
Fax: 781/326-8703
© Analog Devices, Inc., 1999
1 page  
9
6
G = +2
3 RL = 100⍀
0
–3
–6
VS = ؎5V
RFB = 820⍀
VS = ؎5V
RFB = 1k⍀
–9
–12
10M
100M
FREQUENCY – Hz
1G
Figure 10. Frequency Response, G = +2
0.1
0
–0.1
RF = 698⍀
RF =
649⍀
–0.2
–0.3
G = +2
–0.4
–0.5
RL = 100⍀
VIN = 50mV
RF = 750⍀
–0.6
–0.7
–0.8
–0.9
1M
10M
FREQUENCY – Hz
100M
Figure 11. 0.1 dB Flatness, R Package (for N Package Add
50 Ω to RF)
–50
VOUT = 2V p-p
–60 RL = 1k⍀
G = +2
؎5V SUPPLIES
–70
2ND HARMONIC
–80
–90
–100
3RD HARMONIC
–110
10k
100k
1M
FREQUENCY – Hz
10M
100M
Figure 12. Distortion vs. Frequency, RL = 1 kΩ
1000
800
600
400
200
VS = ؎5V
RL = 100⍀
G = +2
R
PACKAGE
AD8001
N
PACKAGE
0
500 600 700 800 900
VALUE OF FEEDBACK RESISTOR (RF) – ⍀
Figure 13. –3 dB Bandwidth vs. RF
1000
–50
؎5V SUPPLIES
–60 VOUT = 2V p-p
RL = 100⍀
G = +2
–70
2ND HARMONIC
–80
–90
3RD HARMONIC
–100
10k
100k
1M
FREQUENCY – Hz
10M
100M
Figure 14. Distortion vs. Frequency, RL = 100 Ω
0.08
0.06
0.04
0.02
0.00
0.02
0.01
0.00
–0.01
–0.02
G = +2
RF = 806⍀
2 BACK TERMINATED
LOADS (75⍀)
1 BACK TERMINATED
LOAD (150⍀)
1 AND 2 BACK TERMINATED
LOADS (150⍀ AND 75⍀)
0 100
IRE
Figure 15. Differential Gain and Differential Phase
REV. C
–5–
5 Page 
AD8001
Printed Circuit Board Layout Considerations
As to be expected for a wideband amplifier, PC board parasitics
can affect the overall closed-loop performance. Of concern are
stray capacitances at the output and the inverting input nodes. If
a ground plane is to be used on the same side of the board as
the signal traces, a space (5 mm min) should be left around the
signal lines to minimize coupling. Additionally, signal lines
connecting the feedback and gain resistors should be short
enough so that their associated inductance does not cause high
frequency gain errors. Line lengths on the order of less than
5 mm are recommended. If long runs of coaxial cable are being
driven, dispersion and loss must be considered.
Power Supply Bypassing
Adequate power supply bypassing can be critical when optimiz-
ing the performance of a high frequency circuit. Inductance in
the power supply leads can form resonant circuits that produce
peaking in the amplifier’s response. In addition, if large current
transients must be delivered to the load, then bypass capacitors
(typically greater than 1 µF) will be required to provide the best
settling time and lowest distortion. A parallel combination of
4.7 µF and 0.1 µF is recommended. Some brands of electrolytic
capacitors will require a small series damping resistor ≈4.7 Ω for
optimum results.
DC Errors and Noise
There are three major noise and offset terms to consider in a
current feedback amplifier. For offset errors refer to the equa-
tion below. For noise error the terms are root-sum-squared to
give a net output error. In the circuit below (Figure 43) they are
input offset (VIO) which appears at the output multiplied by the
noise gain of the circuit (1 + R F/RI), noninverting input current
(IBN × RN) also multiplied by the noise gain, and the inverting
input current, which when divided between RF and RI and sub-
sequently multiplied by the noise gain always appears at the
output as IBN × RF. The input voltage noise of the AD8001 is a
low 2 nV/√Hz. At low gains though the inverting input current
noise times RF is the dominant noise source. Careful layout and
device matching contribute to better offset and drift specifica-
tions for the AD8001 compared to many other current feedback
amplifiers. The typical performance curves in conjunction with
the equations below can be used to predict the performance of
the AD8001 in any application.
VOUT
= VIO × 1 +
RF
±
I BN
× RN
× 1 +
RF
±
I BI
× RF
RI
RI
RF
RI IBI
RN IBN
VOUT
Driving Capacitive Loads
The AD8001 was designed primarily to drive nonreactive loads.
If driving loads with a capacitive component is desired, best
frequency response is obtained by the addition of a small series
resistance as shown in Figure 44. The accompanying graph
shows the optimum value for RSERIES vs. capacitive load. It is
worth noting that the frequency response of the circuit when
driving large capacitive loads will be dominated by the passive
roll-off of RSERIES and CL.
909⍀
RSERIES
IN
RL
500⍀
CL
Figure 44. Driving Capacitive Loads
40
G = +1
30
20
10
0
0 5 10 15 20 25
CL – pF
Figure 45. Recommended RSERIES vs. Capacitive Load
Figure 43. Output Offset Voltage
REV. C
–11–
11 Page | ||
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