PDF 5962-9312901M2A Data sheet ( Hoja de datos )

Número de pieza	5962-9312901M2A
Descripción	High-Speed/ Low-Noise Video Op Amp
Fabricantes	Analog Devices
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No Preview Available ! a High-Speed, Low-Noise Video Op Amp AD829 FEATURES High Speed 120 MHz Bandwidth, Gain = –1 230 V/␮s Slew Rate 90 ns Settling Time to 0.1% Ideal for Video Applications 0.02% Differential Gain 0.04؇ Differential Phase Low Noise 1.7 nV/√Hz Input Voltage Noise 1.5 pA/√Hz Input Current Noise Excellent DC Precision 1 mV max Input Offset Voltage (Over Temp) 0.3 ␮V/؇C Input Offset Drift Flexible Operation Specified for ؎5 V to ؎15 V Operation ؎3 V Output Swing into a 150 ⍀ Load External Compensation for Gains 1 to 20 5 mA Supply Current Available in Tape and Reel in Accordance with EIA-481A Standard PRODUCT DESCRIPTION The AD829 is a low noise (1.7 nV/√Hz), high speed op amp with custom compensation that provides the user with gains from ± 1 to ± 20 while maintaining a bandwidth greater than 50 MHz. The AD829’s 0.04° differential phase and 0.02% differential gain performance at 3.58 MHz and 4.43 MHz, driving reverse-terminated 50 Ω or 75 Ω cables, makes it ideally suited for professional video applications. The AD829 achieves its 230 V/µs uncompensated slew rate and 750 MHz gain band- width product while requiring only 5 mA of current from the power supplies. The AD829’s external compensation pin gives it exceptional versatility. For example, compensation can be selected to opti- mize the bandwidth for a given load and power supply voltage. As a gain-of-two line driver, the –3 dB bandwidth can be in- creased to 95 MHz at the expense of 1 dB of peaking. In addi- tion, the AD829’s output can also be clamped at its external compensation pin. The AD829 has excellent dc performance. It offers a minimum open-loop gain of 30 V/mV into loads as low as 500 Ω, low input voltage noise of 1.7 nV/√Hz, and a low input offset volt- age of 1 mV maximum. Common-mode rejection and power supply rejection ratios are both 120 dB. The AD829 is also useful in multichannel, high speed data conversion where its fast (90 ns to 0.1%) settling time is of importance. In such applications, the AD829 serves as an input buffer for 8-to-10-bit A/D converters and as an output I/V con- verter for high speed D/A converters. REV. E Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. CONNECTION DIAGRAMS 8-Lead Plastic Mini-DIP (N), Cerdip (Q) and SOIC (R) Packages OFFSET NULL 1 AD829 8 OFFSET NULL –IN 2 7 +VS +IN 3 6 OUTPUT –VS 4 TOP VIEW (Not to Scale) 5 CCOMP 20-Lead LCC Pinout 3 2 1 20 19 NC 4 –IN 5 NC 6 +IN 7 NC 8 AD829 TOP VIEW (Not to Scale) 18 NC 17 +V 16 NC 15 OUTPUT 14 NC 9 10 11 12 13 NC = NO CONNECT The AD829 provides many of the same advantages that a trans- impedance amplifier offers, while operating as a traditional voltage feedback amplifier. A bandwidth greater than 50 MHz can be maintained for a range of gains by changing the external compensation capacitor. The AD829 and the transimpedance amplifier are both unity gain stable and provide similar voltage noise performance (1.7 nV/√Hz). However, the current noise of the AD829 (1.5 pA/√Hz) is less than 10% of the noise of trans- impedance amps. Furthermore, the inputs of the AD829 are symmetrical. PRODUCT HIGHLIGHTS 1. Input voltage noise of 2 nV/√Hz, current noise of 1.5 pA/ √Hz and 50 MHz bandwidth, for gains of 1 to 20, make the AD829 an ideal preamp. 2. Differential phase error of 0.04° and a 0.02% differential gain error, at the 3.58 MHz NTSC and 4.43 MHz PAL and SECAM color subcarrier frequencies, make it an outstanding video performer for driving reverse-terminated 50 Ω and 75 Ω cables to ± 1 V (at their terminated end). 3. The AD829 can drive heavy capacitive loads. 4. Performance is fully specified for operation from ± 5 V to ± 15 V supplies. 5. Available in plastic, cerdip, and small outline packages. Chips and MIL-STD-883B parts are also available. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781/329-4700 World Wide Web Site: http://www.analog.com Fax: 781/326-8703 © Analog Devices, Inc., 2000 1 page 120 +100 PHASE 100 +80 GAIN ؎15V 80 Supplies +60 1k⍀ Load 60 GAIN ؎5V Supplies 40 500⍀ Load +40 +20 CCOMP = 0pF 20 0 0 –20 100 1k 10k 100k 1M 10M 100M FREQUENCY – Hz Figure 10. Open-Loop Gain & Phase Margin vs. Frequency 105 100 VS = ؎15V 95 90 VS = ؎5V 85 80 75 10 100 1k LOAD RESISTANCE – ⍀ 10k Figure 11. Open-Loop Gain vs. Resistive Load AD829 120 +SUPPLY 100 80 – SUPPLY 60 40 CCOMP = 0pF 20 1k 10k 100k 1M 10M FREQUENCY – Hz 100M Figure 12. Power Supply Rejection Ratio (PSRR) vs. Frequency 120 100 80 60 CCOMP = 0pF 40 20 1k 10k 100k 1M 10M FREQUENCY – Hz 100M Figure 13. Common-Mode Rejection Ratio vs. Frequency 30 25 VS = ±15V 20 RL = 1k⍀ AV = +20 15 VS = ±5V RL = 500⍀ 10 AV = +20 CCOMP = 0pF 5 CCOMP = 0pF 0 1 10 100 INPUT FREQUENCY – MHz Figure 14. Large Signal Frequency Response 10 8 6 4 2 0 –2 –4 –6 –8 –10 0 1% 0.1% 1% 0.1% ERROR AV = –19 CCOMP = 0pF 20 40 60 80 100 120 140 160 SETTLING TIME – ns Figure 15. Output Swing & Error vs. Settling Time –70 VIN = 3V RMS –75 AV = –1 CCOMP = 30pF –80 CLOAD = 100pF –85 RL = 500⍀ –90 –95 –100 –105 RL = 2k⍀ –110 100 300 1k 3k 10k 30k 100k FREQUENCY – Hz Figure 16. Total Harmonic Dis- tortion (THD) vs. Frequency –20 VIN = 2.24V RMS 3rd HARMONIC –30 AV = –1 RL = 250⍀ CLOAD = 0 –40 CCOMP = 30pF –50 2nd HARMONIC –60 –70 0 500k 1M 1.5M FREQUENCY – Hz 2M Figure 17. 2nd & 3rd Harmonic Distortion vs. Frequency 5 4 3 2 1 0 10 100 1k 10k 100k 1M 10M FREQUENCY – Hz Figure 18. Input Voltage Noise Spectral Density REV. E –5– 5 Page AD829 –17 –20 –23 ؎5V –26 ؎15V –29 –32 –35 –38 –41 –44 –47 1M VIN = –20dBM RL = 1k⍀ RF = 1k⍀ GAIN = –1 CCOMP = 4pF 10M FREQUENCY – Hz 100M Figure 35. Closed-Loop Frequency Response vs. Supply for the Inverting Amplifier Using Current Feedback Compensation A Low Error Video Line Driver The buffer circuit shown in Figure 37 will drive a back-termi- nated 75 Ω video line to standard video levels (1 V p-p) with 0.1 dB gain flatness to 30 MHz with only 0.04° and 0.02% differential phase and gain at the 4.43 MHz PAL color subcarrier frequency. This level of performance, which meets the requirements for high definition video displays and test equipment, is achieved using only 5 mA quiescent current. A High Gain, Video Bandwidth Three Op Amp In Amp Figure 38 shows a three op amp instrumentation amplifier cir- cuit which provides a gain of 100 at video bandwidths. At a circuit gain of 100 the small signal bandwidth equals 18 MHz into an FET probe. Small signal bandwidth equals 6.6 MHz with a 50 Ω load. 0.1% settling time is 300 ns. +VIN 3pF (G = 20) A1 2–8pF SETTLING TIME AC CMR ADJUST +15V 0.1␮F 50⍀ COAX CABLE VIN AD829 50⍀ 50⍀ COAX 50⍀ CABLE VOUT –15V 0.1␮F 3pF CCOMP 2k⍀ 50⍀ 2k⍀ Figure 36. Noninverting Amplifier Connection Using Current Feedback Compensation 0.1␮F +15V VIN AD829 75⍀ 75⍀ COAX 75⍀ CABLE VOUT 75⍀ 30pF CCOMP 0.1␮F 300⍀ –15V OPTIONAL 2 – 7pF FLATNESS TRIM 300⍀ Figure 37. A Video Line Driver with a Flatness over Frequency Adjustment The input amplifiers operate at a gain of 20, while the output op amp runs at a gain of 5. In this circuit the main bandwidth limitation is the gain/ bandwidth product of the output ampli- fier. Extra care needs to be taken while breadboarding this cir- cuit, since even a couple of extra picofarads of stray capacitance at the compensation pins of A1 and A2 will degrade circuit bandwidth. RG 210⍀ +VIN AD829 2k⍀ 1pF 200⍀ 1k⍀ AD848 1pF 2k⍀ AD829 A2 (G = 20) 3pF 200⍀ A3 3pF 970⍀ DC CMR ADJUST 50⍀ (G = 5) ( (CIRCUIT GAIN = 4000⍀ RG +1 5 2k⍀ +15V COMM –15V INPUT FREQUENCY CMRR 100 Hz 1 MHz 10 MHz 64.6dB 44.7dB 23.9dB 10␮F 0.1␮F +VS 1␮F 10␮F 0.1␮F –VS 1␮F Figure 38. A High Gain, Video Bandwidth Three Op Amp In Amp Circuit PIN 7 0.1␮F EACH 0.1␮F AMPLIFIER PIN 4 REV. E –11– 11 Page

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