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PDF ISL9103 Data sheet ( Hoja de datos )
| Número de pieza | ISL9103 | |
| Descripción | 500mA 2.4MHz Low IQ High Efficiency Synchronous Buck Converter | |
| Fabricantes | Intersil | |
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Data Sheet
ISL9103, ISL9103A
December 9, 2015
FN6828.3
500mA 2.4MHz Low IQ High Efficiency
Synchronous Buck Converter
The ISL9103, ISL9103A is a 500mA, 2.4MHz step-down
regulator, which is ideal for powering low-voltage
microprocessors in compact devices such as PDAs and
cellular phones. It is optimized for generating low output
voltages down to 0.8V. The supply voltage range is from
2.7V to 6V allowing the use of a single Li+ cell, three NiMH
cells or a regulated 5V input. It has guaranteed minimum
output current of 500mA. A high switching frequency of
2.4MHz pulse-width modulation (PWM) allows using small
external components. Under light load condition, the device
operates at low IQ skip mode with typical 20µA quiescent
current for highest light load efficiency to maximize battery
life, and it automatically switches to fixed frequency PWM
mode under heavy load condition.
The ISL9103, ISL9103A includes a pair of low
ON-resistance P-Channel and N-Channel internal MOSFETs
to maximize system efficiency and minimize the external
component count. 100% duty-cycle operation allows less
than 300mV dropout voltage at 500mA.
The ISL9103, ISL9103A offers internal digital soft-start,
enable for power sequence, overcurrent protection and
thermal shutdown functions. In addition, the ISL9103,
ISL9103A offers a quick bleeding function that discharges
the output capacitor when the IC is disabled.
The ISL9103, ISL9103A is offered in a 1.6x1.6mm UTDFN
package. The complete converter occupies less than
0.5cm2.
Pinout
ISL9103, ISL9103A
(6 LD 1.6x1.6 UTDFN)
TOP VIEW
VIN 1
EN 2
NC 3
6 SW
5 GND
4 FB
Features
• High Efficiency Integrated Synchronous Buck Regulator
with up to 95% Efficiency
• 2.7V to 6.0V Supply Voltage
• 2.4MHz PWM Switching Frequency
• 500mA Guaranteed Output Current
• 3% Output Accuracy Over-Temperature and Line for Fixed
Output Options
• 20µA Quiescent Supply Current in Skip Mode
• Less than 1µA Logic Controlled Shutdown Current
• 100% Maximum Duty Cycle for Lowest Dropout
• Ultrasonic Switching Frequency at Skip Mode to Prevent
Audible Frequency Noise (For ISL9103A Only)
• Discharge Output Capacitor when Disabled
• Internal Digital Soft-Start
• Peak Current Limiting, Short Circuit Protection
• Over-Temperature Protection
• Chip Enable
• Small 6 Pin 1.6mmx1.6mm UTDFN Package
• Pb-Free (RoHS Compliant)
Applications
• Single Li-ion Battery-Powered Equipment
• Mobile Phones and MP3 Players
• PDAs and Palmtops
• WCDMA Handsets
• Portable Instruments
1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Copyright Intersil Americas LLC 2009, 2015. All Rights Reserved
Intersil (and design) is a trademark owned by Intersil Corporation or one of its subsidiaries.
All other trademarks mentioned are the property of their respective owners.
1 page  
ISL9103, ISL9103A
Typical Operating Performance (Continued)
2.520
2.515
2.510
VIN = 4.0V, RISING
2.505
2.500
VIN = 4.0V, FALLING
2.4950
100 200 300 400
IOUT(mA)
FIGURE 5. OUTPUT VOLTAGE vs LOAD CURRENT
(ISL9103, VO_NORMINAL = 2.5V)
500
5V/DIV
1V/DIV
VSW
VOUT
200mA/DIV
5V/DIV
IL
EN
FIGURE 6. SOFT-START TO PFM MODE (VIN = 3.6V,
VOUT = 1.5V, IOUT = 0.001mA)
5V/DIV
1V/DIV
500mA/DIV
5V/DIV
VSW
VOUT
IL
EN
FIGURE 7. SOFT-START TO PWM MODE (VIN = 3.6V,
VOUT = 1.5V, IOUT = 500mA)
5V/DIV
2V/DIV
VSW
VOUT
200mA/DIV
5V/DIV
IL
EN
FIGURE 8. SOFT-START TO PFM MODE (VIN = 3.6V,
VOUT = 2.5V, IOUT = 0.001mA)
5V/DIV
VSW
50mV/DIV
VOUT
20mA/DIV
Io
FIGURE 9. LOAD TRANSIENT IN PFM MODE (VIN = 3.6V,
VOUT = 1.5V, 5mA TO 30mA)
5
5V/DIV
VSW
50mV/DIV
VOUT
20mA/DIV
Io
FIGURE 10. LOAD TRANSIENT IN PFM MODE (VIN = 3.6V,
VOUT = 1.5V, 30mA TO 5mA)
FN6828.3
December 9, 2015
5 Page 
ISL9103, ISL9103A
Overcurrent Protection
The overcurrent protection is provided on ISL9103, ISL9103A
when overload condition happens. It is realized by monitoring
the CSA output with the OCP comparator, as shown in
Figure 22. When the current at P-Channel MOSFET is sensed
to reach the current limit, the OCP comparator is triggered to
turn off the P-Channel MOSFET immediately.
Short-Circuit Protection
ISL9103, ISL9103A has a Short-Circuit Protection (SCP)
comparator, which monitors the FB pin voltage for output
short-circuit protection. When the output voltage is sensed to
be lower than a certain threshold, the SCP comparator
reduces the PWM oscillator frequency to a much lower
frequency to protect the IC from being damaged.
Undervoltage Lockout (UVLO)
When the input voltage is below the Undervoltage Lock Out
(UVLO) threshold, ISL9103, ISL9103A is disabled.
Soft-Start
The soft-start feature eliminates the inrush current during the
circuit start-up. The soft-start block outputs a ramp reference
to both the voltage loop and the current loop. The two ramps
limit the inductor current rising speed as well as the output
voltage speed so that the output voltage rises in a controlled
fashion.
Low Dropout Operation
The ISL9103, ISL9103A features low dropout operation to
maximize the battery life. When the input voltage drops to a
level that ISL9103, ISL9103A can no longer operate under
switching regulation to maintain the output voltage, the
P-Channel MOSFET is completely turned on (100% duty
cycle). The dropout voltage under such condition is the
product of the load current and the ON-resistance of the
P-Channel MOSFET. Minimum required input voltage VIN
under this condition is the sum of output voltage plus the
voltage drop cross the inductor and the P-Channel MOSFET
switch.
Thermal Shut Down
The ISL9103, ISL9103A provides built-in thermal protection
function. The thermal shutdown threshold temperature is
+130°C (typ) with a 30°C (typ) hysteresis. When the internal
temperature is sensed to reach +130°C, the regulator is
completely shut down and as the temperature drops to
+100°C (typ), the ISL9103, ISL9103A resumes operation
starting from the soft-start.
Applications Information
Inductor and Output Capacitor Selection
To achieve better steady state and transient response,
ISL9103, ISL9103A typically uses a 2.2µH inductor. The
peak-to-peak inductor current ripple can be expressed in
Equation 1:
I = V-----O--------L----1-----f–--S---V--V-------I--O--N-------
(EQ. 1)
In Equation 1, usually the typical values can be used but to
have a more conservative estimation, the inductance should
consider the value with worst case tolerance; and for
switching frequency fS, the minimum fS from the “Electrical
Specifications” table on page 3 can be used.
To select the inductor, its saturation current rating should be
at least higher than the sum of the maximum output current
and half of the delta calculated from Equation 1. Another
more conservative approach is to select the inductor with the
current rating higher than the P-Channel MOSFET peak
current limit.
Another consideration is the inductor DC resistance since it
directly affects the efficiency of the converter. Ideally, the
inductor with the lower DC resistance should be considered
to achieve higher efficiency.
Inductor specifications could be different from different
manufacturers so please check with each manufacturer if
additional information is needed.
For the output capacitor, a ceramic capacitor can be used
because of the low ESR values, which helps to minimize the
output voltage ripple. A typical value of 10µF ceramic
capacitor should be enough for most of the applications and
the capacitor should be X5R or X7R.
Input Capacitor Selection
The main function for the input capacitor is to provide
decoupling of the parasitic inductance and to provide filtering
function to prevent the switching current from flowing back to
the battery rail. A 10µF ceramic capacitor (X5R or X7R) is a
good starting point for the input capacitor selection.
Output Voltage Setting Resistor Selection
For ISL9103, ISL9103A adjustable output option, the voltage
resistors, R1 and R2, as shown in Figure 21, set the desired
output voltage values. The output voltage can be calculated
using Equation 2:
VO
=
VFB
1
+
RR-----12-
(EQ. 2)
where VFB is the feedback voltage (typically it is 0.8V). The
current flowing through the voltage divider resistors can be
calculated as VO/(R1 + R2), so larger resistance is desirable
to minimize this current. On the other hand, the FB pin has
leakage current that will cause error in the output voltage
setting. The leakage current has a typical value of 0.1µA. To
minimize the accuracy impact on the output voltage, select
the R2 no larger than 200k.
11 FN6828.3
December 9, 2015
11 Page | ||
| Páginas | Total 14 Páginas | |
| PDF Descargar | [ Datasheet ISL9103.PDF ] | |
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